LC controllable oscillator, a quadrature oscillator and a communication arrangement

ABSTRACT

A LC controllable oscillator (LCCO) according to the invention comprises a voltage-controlled oscillator (VCO) and a first voltage controlled current source (VCCS) of a first type for supplying a current to the VCO. The VCO is realized with a flit pair of VCCCS of the first type coupled with a second paw of VCCS of a second type end a LC resonator. The VCO generates a periodical oscillation frequency that is controllable by a control signal (V). The LCCO further comprises a replica scaled bias module (RSBM) supplied from the external voltage source. The RSBM is conceived to generate a control signal (BIAS CONTROL) for controlling the supplied current delivered by the first VCCS to the VCO.

FIELD OF THE INVENTION

The invention relates to a LC controllable oscillator (LCCO) comprisinga voltage controlled oscillator (VCO), a first voltage controlledcurrent source (VCCS) of a first type for supplying a current to theVCO, the VCO being realized with a first pair of VCCS of the first typecoupled with a second pair of VCCS of a second type and a LC resonatoradapted to be controlled for generating a periodical oscillationfrequency which is controllable by a control signal (V), furthercomprising a first (SUP) conductor and a second (REF) conductor forconnection to an external direct voltage source (VS).

The invention further relates to a module and an arrangement that usesthe LCCO.

BACKGROUND OF THE INVENTION

The following is defined in this description: if a VCCS of the firsttype is considered that sources it's output current then a VCCS of thesecond type sinks it's output current. Furthermore, if a VCCS of thefirst type is considered that sinks it's output current then a VCCS ofthe second type sources it's output current.

LC oscillators are well known circuits that are used in a large spectrumof applications for generating periodical signals. When they are used inhigh frequency applications as optical fiber networks, mobile telephony,transceivers and many others, they must provide, among other qualities,a good stability of the periodical signals versus temperaturemodification, they must be controllable over a wide frequency range ofthe periodical signals, and so on.

The LC oscillators are preferred in high frequency applications becauseof their frequency accuracy and reduced phase margin noise they exhibit.These LC oscillators have as their main components a pair of activedevices, transistors for example and a LC tank circuit that determinestheir oscillation frequency.

Such an oscillator is disclosed in U.S. Pat. No. 5,959,504. It comprisesa first pair of CMOS transistors with a tunable voltage applied to theback gate terminals for varying the parasitic capacitance of thetransistor pair. The circuit further comprises a current generatingmeans or a second transistor pair having a similar configuration but ofopposite polarity to the first transistor pair that is connected to thefirst transistor pair and across an inductor. The frequency of theoscillation is determined by the product between the inductor inductanceand the parasitic capacitance of the first pair of transistors. Itshould be pointed out here that the oscillation frequency is determinedby technology dependent parameters as the CMOS parasitic capacitance andthe frequency is controlled with a voltage applied at the back gate ofthe CMOS transistors, being dependent on a specific type of activedevice. Furthermore no measures are considered for thermallycompensation of the oscillator.

SUMMARY OF THE INVENTION

It is therefore an object of the present invention to provide a LCoscillator with means to improve the temperature behavior of thefrequency of the oscillation, the frequency of oscillation beingdetermined independently of the technology.

In accordance with the invention this is achieved in a device asdescribed in introductory paragraph characterized in that the LCCOfurther comprises a replica scaled bias module (RSBM) supplied from theexternal voltage source via the first conductor (SUP) and the secondconductor (REF), the RSBM being conceived to generate a control signal(BIAS CONTROL) for controlling the supplied current delivered by thefirst VCCS to the VCO.

The LCCO according to the invention has the advantage of a frequencyindependent of technology and a better thermal stabilization.

In an embodiment of the invention the RSBM comprises a second, a thirdand a fourth VCCS, the second and the third VCCS being of the firsttype, the fourth VCCS being of the second type.

The VCCS used in the RSBM are replicas at a different scale of that usedin the VCO, the currents circulating through them being proportional toeach other. For example, if a current sourced or sinked by a VCCS is I₀then the replica scaled VCCS sources or sinks a current I₀/m, m beingthe scale factor.

The BIAS CONTROL signal modifies in the same way the supply current ofthe VCO and it's replica current in the RSBM module with the process andtemperature variations. In this way the common mode voltage of the firstpair of VCCS and of the second pair of VCCS is maintained constant. Thisimproves the thermal stability and the phase noise margin of the LCCO.

In an embodiment the RSBM further comprises a current source of thefirst type coupled with a fifth VCCS of second type for providing areference voltage to a first input of a differential voltage controlledvoltage source (VCVS).

A second input of the VCVS is coupled with the fourth VCCS for supplyingthe signal (BIAS CONTROL) for controlling the supplied current in theVCO.

It should be pointed out here that the current source and the fifth VCCSmay be regarded as a band gap reference voltage source that provides abetter temperature behavior of the circuit. Furthermore, if the controlsignal V is generated using this band gap reference voltage, theoscillation frequency stability versus temperature is improved, too.

In a preferred embodiment of the invention, a LC tank circuit determinesthe frequency of oscillation that is controlled by an external controlsignal (V). The L and C components of the tank circuit have theirinductance and capacitance much bigger than any other parasiticinductance and capacitance in the circuit and, as a matter ofconsequence, the oscillation frequency is determined independently ofthe technology.

It should be pointed out here that depending on the type the L and Ccomponents of the LC tank circuit it's oscillation frequency can becontrolled electrically, mechanically, thermally, optically.

Illustratively, all the previously described stages may be realized withtransistors and LC tank resonators. In an embodiment all thesetransistors may be implemented in CMOS technology.

It is another object of the present invention to provide a modulecomprising the LCCO coupled with a phase shifter, controlled by thecontrol signal (V), the phase shifter providing a first intermediatesignal (S1) and a second intermediate signal (S2) to an adder (SUM), inwhich the intermediate signals S1 and S2 are added to each other forobtaining a signal (S) that is amplified by a first wide band amplifier(TIA) obtaining a first output signal (I), and to a subtraction circuit(DIF) where the intermediate signals S1 and S2 are subtracted from eachother for obtaining a signal (D) that is amplified by a second wide bandamplifier for obtaining a second output signal (Q).

The module is characterized in that the signals S1 and S2 are mutuallyphase shifted with 90 degrees.

The module is further characterized in that the output signals (I) and(Q) are periodical and mutually in quadrature.

Furthermore it is another object of the present invention to provide acommunication arrangement for communicating via a bi-directionalcommunication channel, characterized in that it comprises a receiverthat comprises a data and clock recovery (DCR) circuit comprising amodule as claimed in claim 6, the receiver being arranged for generatingan output vector of signals by combining a received signal (IN) receivedfrom the channel with the periodical signals (I) and (Q), thearrangement further comprising an emission module for emitting anemission signal (OUT) to the channel, the emission module generating theemission signal by combining the periodical signals (I) and (Q) with aninput signal vector (IN1) in a phase locked loop (PLL) circuit thatcontains the module.

The above and other features and advantages of the invention will beapparent from the following description of exemplary embodiments of theinvention with reference to the accompanying drawings, in which:

BRIEF DESCRIPTION OF THE DRAWING

FIG. 1 depicts a block diagram of a LC controllable oscillator (LCCO),according to the invention,

FIG. 2 depicts a more detailed diagram of the LCCO according to theinvention,

FIG. 3 depicts a CMOS implementation of the LCCO according to oneembodiment of the invention,

FIG. 4 depicts a module that uses a LCCO,

FIG. 5 depicts a communication arrangement for communicating via abi-directional channel,

FIG. 6 depicts an interleaved phase/frequency detector in anotherembodiment of the invention,

FIG. 7 depicts a portion of a delay line used in phase shifter,according to the invention,

FIG. 8 depicts a delay lines arrangement used in phase shifter,according to the invention,

FIG. 9 depicts a LC tank circuit used in the phase shifter, according tothe invention.

DETAILED DESCRIPTION OF THE PRIMARY EMBODIMENT

FIG. 1 shows the block diagram of a LC controllable oscillator (LCCO),according to the invention. There is a voltage controlled oscillator(VCO) 102 which is supplied with a current 104 via a VCCS 101 of a firsttype. The current 104 is controlled by a signal BIAS CONTROL supplied bya Replica Scaled Bias module (RSBM) 103. There are also provided twowires, a first wire labeled SUP and a second wire labeled REF to realizea connection between the LCCO and an external direct current source 105.A control signal V controls the oscillation frequency of the LCCO. Ifthe VCCS 101 sources it's output current then the SUP wire is connectedto the positive node of the source 105 and the wire REF is the negativenode of the source 105. If the VCCS 101 sinks it's output current thenthe SUP wire is connected to the negative node of the source 105 and thewire REF is the positive node of the source 105.

FIG. 2 depicts a more detailed diagram of the LCCO according to theinvention. The VCO 102 is realized with a first pair 301 of VCCS of thefirst type and a second pair (302) of VCCS of the second type,comprising a resonator realized, for illustrative purposes, with a LCtank circuit that determines it's oscillation frequency. It is provideda control signal V that controls the oscillation frequency of the LCCO.For illustrative purposes, the control signal is a voltage, butdepending on the practical devices used in the LCCO, it's oscillationfrequency can be modified mechanically, optically, thermally. The LCCOfurther comprises the RSBM 103 comprising a differential voltagecontrolled voltage source (VCVS) 206 having a first input I1 and asecond input I2 and delivers at it's output a signal BIAS CONTROL thatcontrols the supply current 104 of the VCO 102 via the VCCS 101. Acurrent source 205 of the first type coupled with a fifth VCCS 204 ofthe second type in order to provide a first reference voltage at thefirst input I1 of the VCVS 206. The BIAS CONTROL signal also controls acurrent 207 provided by a second VCCS 201 of the first type that iscoupled with a third VCCS 202 of the second type, the third VCCS 202being coupled with a fourth VCCS of the second type 203 and the secondinput terminal of the VCVS 206. The VCCS used in the RSBM are replicasat a different scale of that used in the VCO, the currents circulatingthrough them being proportional each other. For example, if a currentsourced or sinked by a VCCS is 2I₀ then the replica scaled VCCS sourcesor sinks a current 2I₀/m, m being the scale factor. In the case of thecircuit depicted in the FIG. 2 the current 207 is the replica scaled ofthe current 104.

FIG. 3 depicts a CMOS implementation of the LCCO according to oneembodiment of the invention. For illustrative purposes, CMOS transistorswere used. However, the circuit may be implemented either in bipolar,CMOS or BiCMOS technologies, or a combination there of. For bipolartransistors, the control electrode, first main electrode and second mainelectrode correspond to the base, emitter and collector, respectively.For MOS transistors, the control electrode, first main electrode andsecond main electrode correspond to the gate, source and drain,respectively.

The first VCCS 101, the second VCCS 201 and the third VCCS 202 are p-MOStransistors, but any other VCCS of the first type can be used instead.The fourth VCCS 203 and the fifth VCCS 204 are n-MOS transistors but anyother VCCS of the second type can be used instead. The differential VCVS206 is an operational amplifier but any other differential VCVS can beused instead as, for example, an operational transconductance amplifierended on a capacitor, or any other equivalent solutions.

The current 207 through the second VCCS is 2I₀/m and the current throughthe fifth VCCS 204 is I₀/m. Under this circumstances, the BIAS CONTROLsignal generated by the VCVS 206 is proportional to I₀/m which is areplica scaled current that flows through the first pair 301 of VCCS andthe second pair 302 of VCCS in the VCO 102. In this preferred embodimentof the invention the scaling is obtained using transistors with the samelength and with their width scaled with a factor m.

The BIAS CONTROL signal modifies in the same way the supply current 104of the VCO 102 and the replica current 207 in the VCCS 201 with theprocess and temperature variations. In this way the common mode voltageof the first pair (301) of VCCS and of the second pair (302) of VCCS ismaintained constant. This improves considerably the phase noise margin,too. It should be pointed out here that the current source 105 and thefifth VCCS (204) may be replaced with a band gap reference voltagesource that provides a better temperature behavior of the circuit.Furthermore, if the control signal V is generated using this band gapreference voltage, the oscillation frequency stability versustemperature is improved, too.

FIG. 4 depicts a module 300 that uses a LCCO, which is essentially aquadrature oscillator. In the module 300 the LCCO 1 is coupled with aphase shifter 301 and they are controlled simultaneously by the samecontrol signal V. The phase shifter 301 provides a first S1 and a secondS2 intermediate signals at it's outputs that are mutually in quadrature.The phase shifter can be realized as a controllable all pass filter butany other controllable quadrature phase shifter can be used instead. Theintermediate signals S1 and S2 are used as input signals in an adder SUM302 obtaining a signal S and in a subtractor DIF 303 obtaining a signalD. The S signal is amplified with a first amplifier TIA 304 obtaining anoutput signal I and the signal D is amplified with a second amplifierTIA 305 obtaining an output signal Q. The two output signals aremutually in quadrature and, under these circumstances, the module 300 isa quadrature oscillator. In a preferred embodiment of the module the TIA304 and 305 are disclosed in PH-NL010020EPP.

FIG. 5 depicts a communication arrangement 400 for communicating via abi-directional channel 404. The communication arrangement ischaracterized in that it comprises a receiver 401 that comprises a dataand clock recovery DCR circuit 402 comprising the module 300, thereceiver being arranged for generating an output vector of signals OUT1by combining a received signal IN, received from the channel 404, withthe periodical signals I and Q, the arrangement further comprising anemission module 403 for emitting an emission signal OUT to the channel404, the emission module generating the emission signal by combining theperiodical signals I and Q with an input signal vector IN1 in a phaselocked loop PLL circuit 405 that contains the module 300.

In a preferred embodiment of the invention, the output vector OUT1 is avector of signals obtained in a Low IF/Zero IF receivers, SONET/SDHapplications, the input vector of signals IN1 is a suitable codedanalogical signal, the bi-directional communication channel 404 is anoptical network and the arrangement 400 is a transceiver used in opticalcommunication networks.

FIG. 6 depicts an interleaved phase/frequency detector in anotherembodiment of the invention. The LCCO 300 output signals I and Q arecoupled with a first and a second D flip-flops (DFF) 500. The first DFF(500) has an input D1 coupled with an input signal DATA and a Clockinput Ck1 coupled with the signal I from the LCCO generating a signal atan output terminal Q1 which is almost in phase with the positive edge ofthe signal I. The second DFF (500) has an input D2 coupled with an inputsignal DATA and a Clock input Ck2 coupled with the signal Q from theLCCO generating a signal at an output terminal Q2 which is almost inphase with the positive edge of the I signal. The phase/frequencydetector is a part of the DCR 402 and the PLL 405. Furthermore thesignal DATA is a component either of vector IN1 or IN.

FIG. 7 depicts a portion of a delay line 350 used in a phase shifter301, according to the invention. The portion of the delay line 350comprises a plurality of voltage controlled capacitors 351, each of thevoltage controlled capacitors 351 having an anode and a cathode. Thecathodes of the voltage controlled capacitors 351 are coupled to eachother. A capacitance C of the voltage-controlled capacitor 351 iscontrolled via the control voltage V applied to it's cathode. A firstplurality of the anodes of the voltage controlled capacitors 351 iscoupled to a first delay line (1-2), said first delay line (1-2) beingcoupled to a first input terminal 1 and to a first output terminal 2. Asecond plurality of the anodes of the voltage controlled capacitors 351is coupled to a second delay line (1′-2′), said second delay line(1′-2′) being coupled to a second input terminal 1′ and to a secondoutput terminal 2′. (first number-second number) identifies a delay linebetween a terminal labeled with the first number and a terminal labeledwith the second number. A distance between two consecutive anodes ofeither the first portion of delay line (1-2) and the second portion ofdelay line (1′-2′) is identified as d_(i). For instance in FIG. 7 thedistances d₂, d₃ are between two consecutive anodes of two consecutivevoltage controlled capacitors 351. The distance d₁, is between the firstinput terminal 1 and anode of a first anode of a voltage controlledcapacitor 351. The distance d₄ is between a last anode of a voltagecontrolled capacitor 351 and the first output terminal 2. A portion of adelay line could be modeled as a resistor, as an inductor or acombination thereof. The choice of a model or another depends on somephysical characteristics of the delay line as length, width, material ofthe delay line and of the frequency of the signals flowing in the delayline. A portion of a delay line d_(i) could be identified as e.g. aresistor having a resistance R_(i) as an inductor having an inductanceL_(i) or a combination thereof. Both the resistance R_(i) and theinductance L_(i) are proportional to the length of the portion of thedelay line d_(i). A portion of the delay line of length d_(i) coupled toa voltage controlled capacitor 351 is called hereinafter d−C cell. Adelay of a d−C cell could be written as in relation (1). $\begin{matrix}{{{t_{i} \approx {\frac{1}{d_{i}C_{i}}\quad i}} = 1},\quad 2,\quad 3} & (1)\end{matrix}$

In (1) “≈” means “proportional to”. In a particular case the distancesd_(i) could be equal to each other and further equal to d. The voltagecontrolled capacitors 351 could also have a capacitance equal to eachother and equal to C. If N distances d and N voltage controlledcapacitors 351 are considered the total delay is as in relation (2).

t≈Nt_(e)  (2)

where $\begin{matrix}{t_{e} \approx \frac{1}{dC}} & (3)\end{matrix}$

It is further observed that the delay line portion 350 in FIG. 7 is adifferential one being suitable for differential systems. Insingle-ended applications either the terminals 1′ and 2′ or theterminals 1 and 2 are grounded and either the second delay line (1′-2′)or the first delay line (1-2) are replaced by a relatively lowresistance connection respectively.

The portion of delay line 350 shown in FIG. 7 could be used in a phaseshifter 301 as shown in FIG. 8. FIG. 8 depicts a delay lines arrangementused in the phase shifter 301, according to the invention. The delaylines arrangement comprises a first portion of delay line 350 and asecond portion of delay line 350′. The second portion of delay line 350′has a different number of d−C cells than the first portion of delayline. At an output of the phase shifter 301 the first intermediatesignal S1 and the second intermediate signal S2 are obtained. An inputsignal Ph_in is inputted to the first portion of delay line 350 and tothe second portion of delay line 350′, respectively. The input signalPh_in is differently delayed by the portions of delay lines 350 and 350′and a delay difference between the first intermediate signal S1 and thesecond intermediate signal S2 is obtained. The delay difference isequivalent to a phase shift and therefore the first intermediate signalS1 and the second intermediate signal S2 are phase shifted relatively toeach other. A phase shift between the first intermediate signal and thesecond intermediate signal is therefore proportional to the differencein number of d−C cells included in the delay lines portions 350 and350′. For example the first portion of delay line 350 could comprise 5d−C cells and the second portion of delay line 350′ could comprise 1 d−Ccell when SiGe BiCMOS technology is considered. For increasing aflexibility in applications it is desirable that the phase-shift betweenthe first intermediate signal S1 and the second intermediate signal S2to be adjustable for obtaining a precise phase shift e.g. 90 degreesi.e. quadrature signals. This could be achieved using a controllabletank circuit as shown in FIG. 9. The tank circuit comprises an inductorhaving an inductance L coupled to a pair of voltage controlledcapacitors 351 having their cathodes coupled together. The cathodes arefurther coupled to a fine control terminal. A voltage V_(fine) inputtedto the fine control terminal controls the capacitance of the voltagecontrolled capacitors 351. The tank circuit introduces an additionalphase shift to a portion of delay line. The tank circuit is coupled tothe first output terminal 2 and to the second output terminal 2′ ofeither the first portion of delay line 350 or the second portion ofdelay line 350′.

It is remarked that the scope of protection of the invention is notrestricted to the embodiments described herein. Neither is the scope ofprotection of the invention restricted by the reference numerals in theclaims. The word ‘comprising’ does not exclude other parts than thosementioned in a claim. The word ‘a(n)’ preceding an element does notexclude a plurality of those elements. Means forming part of theinvention may both be implemented in the form of dedicated hardware orin the form of a programmed general purpose processor. The inventionresides in each new feature or combination of features.

What is claimed is:
 1. A LC controllable oscillator (LOCO) (1)comprising: a voltage controlled oscillator (VCO) (102), a first voltagecontrolled current source (VCCS) of a first type (101) for supplying acurrent (104) to the VCO (102), the VCO being realized with a first pair(301) of VCCS of the first type coupled with a second pair (302) of VCCSof a second type and a LC resonator adapted for generating a periodicaloscillation frequency which is controllable by a control signal (V), afirst (SUP) conductor and a second (REP) conductor for connection to anexternal direct voltage source (105) characterized in that the LCCO (1)further comprises a replica scaled bias module (RSBM) (103) suppliedfrom the external voltage source (105) via the first conductor (SUP) andthe second conductor (REF), the RSBM (103) is conceived to generate acontrol signal (BIAS CONTROL) for controlling the supplied current (104)delivered by the first VCCS (101) to the VCO (102) and the RSBM (103)further comprises a current source of the first type (205) and a thirdVCCS of the second type (204) that are coupled in a first input node(I1) of a differential voltage controlled voltage source (VCVS) (206)that further comprises a second input (I2) that is coupled with thesecond VCCS (203) for supplying the signal (BIAS CONTROL) forcontrolling the supply current (104) in the VCO (102).
 2. A LCCO (1) asclaimed in claim 1 wherein the RSBM (103) comprises a fourth (201), afifth (202) and the second (203) VCCS, the fourth and fifth VCCS beingof the first type, the second VCCS being of the second type.
 3. A module(300) comprising a LOCO (1) as claimed in claim 1 coupled with a phaseshifter (301), controlled by the control signal (V), the phase shifter(301) being conceived to provide a first intermediate signal (S1) and asecond intermediate signal (S2) to an adder (SUM) (302), for adding theintermediate signals S1 and S2 to each other for obtaining a signal (S)to be supplied to a first wide band amplifier (TIA) (304) for obtaininga first output signal (I), and to a subtraction circuit (DIF) (303) forsubtracting the intermediate signals S1 and S2 from each other forobtaining a signal (D) to be supplied to a second wide band amplifier(TIA) (305) for obtaining a second output signal (Q).
 4. A module (300)as claimed in claim 3 characterized in that the first and secondintermediate signals S1 and S2 are mutually phase shifted with 90degrees.
 5. A module (300) as claimed in claim 3 characterized in thatthe output signals (I) and (Q) are periodical and mutually inquadrature.
 6. A communication arrangement (400) for communicating via abi-directional communication channel (404), characterized in that itcomprises a receiver (401) that comprises a data and clock recovery(DCR) circuit (402) comprising a module (300) as claimed in claim 5, thereceiver being arranged for generating an output vector of signals(OUT1) by combining a received signal (IN) received from thebi-directional communication channel (404) with the periodical signals(I) and (Q), the arrangement further comprising an emission module (403)for emitting an emission signal (OUT) to the bi-directionalcommunication channel (404), the emission module being conceived togenerate the emission signal by combining the periodical signals (I) and(Q) with an input signal vector (IN1) in a phase locked loop (PLL)circuit (405) that contains the module (300).